Modulation and Demodulation for Enhanced Noise Margins in 5G and 6G

ABSTRACT

Message faults are expected to become a major problem for next-generation 5G/6G networks, due to signal fading, high backgrounds, and high density of users. Disclosed are methods to modulate and demodulate messages to optimize noise margins, greatly enhancing reliability at negligible cost, according to some embodiments. A transmitter can modulate a message using amplitude-phase modulation, yet a receiver can conveniently receive and process the signals according to separate in-phase (I) and quad-phase (Q) branches, that is, according to QAM. The receiver can then convert the I and Q values to the original waveform amplitude and phase mathematically, and then demodulate those values using predetermined amplitude and phase levels as provided by a proximate demodulation reference. By converting the as-received QAM values to the as-transmitted amplitude-phase values, the receiver can thereby avoid many noise vulnerabilities inherent in QAM-modulated messages, and thereby obtain the full noise margins provided by amplitude-phase modulation.

PRIORITY CLAIMS AND RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No.17/212,905, entitled “Demodulation Using Two Modulation Schemes in 5Gand 6G”, filed Jun. 22, 2023, which is a continuation of U.S. patentapplication Ser. No. 17/994,876, entitled “Multiplexed Amplitude-PhaseModulation for 5G/6G Noise Mitigation”, filed Nov. 28, 2022, whichclaims the benefit of U.S. Provisional Patent Application Ser. No.63/426,853, entitled “Multiplexed Amplitude-Phase Modulation for 5G/6GNoise Mitigation”, filed Nov. 22, 2022, and U.S. Provisional PatentApplication Ser. No. 63/418,784, entitled “Demodulation for Phase-NoiseMitigation in 5G and 6G”, filed Oct. 24, 2022, and U.S. ProvisionalPatent Application Ser. No. 63/412,654, entitled “Guard-SpacePhase-Tracking Reference Signal for 5G and 6G Networking”, filed Oct. 3,2022, and U.S. Provisional Patent Application Ser. No. 63/403,924,entitled “Phase-Noise Mitigation at High Frequencies in 5G and 6G”,filed Sep. 6, 2022, and U.S. Provisional Patent Application Ser. No.63/409,888, entitled “Single-Branch Reference for High-Frequency PhaseTracking in 5G and 6G”, filed Sep. 26, 2022, and U.S. Provisional PatentApplication Ser. No. 63/321,879, entitled “Low-Complexity Demodulationof 5G and 6G Messages”, filed Mar. 21, 2022, and U.S. Provisional PatentApplication Ser. No. 63/309,748, entitled “Error Detection andCorrection in 5G/6G Pulse-Amplitude Modulation”, filed Feb. 14, 2022,all of which are hereby incorporated by reference in their entireties.

FIELD OF THE INVENTION

The disclosure pertains to mitigation of amplitude noise and phase noisein wireless messaging, and particularly to phase-noise mitigation athigh frequencies.

BACKGROUND OF THE INVENTION

Wireless communication at very high frequencies, such as tens tohundreds of GHz, is needed for the massively increased demand inbandwidth and throughput expected in 5G and 6G. However, phase noise isan increasing problem at higher frequencies, preventing full usage ofthe bandwidth for messaging. What is needed is means for mitigating thephase noise so that the promise of high-speed messaging at highfrequencies can be at least partially realized.

This Background is provided to introduce a brief context for the Summaryand Detailed Description that follow. This Background is not intended tobe an aid in determining the scope of the claimed subject matter nor beviewed as limiting the claimed subject matter to implementations thatsolve any or all of the disadvantages or problems presented above.

SUMMARY OF THE INVENTION

In a first aspect, there is a method for a wireless receiver todemodulate a message, the method comprising: receiving a demodulationreference modulated, by a transmitter, according to an amplitude-phasemodulation scheme comprising Namp amplitude levels and Nphase phaselevels; determining, according to the demodulation reference, the Nampamplitude levels and the Nphase phase levels of the modulation scheme;receiving a message modulated, by the transmitter, according to theamplitude-phase modulation scheme, the message comprising messageelements, each message element comprising a resource element of aresource grid, wherein each message element, as received by the wirelessreceiver, contains a received wave comprising a received wave amplitudeand a received wave phase; for each message element, separating thereceived wave into an I-branch and an orthogonal Q-branch, the I-branchcomprising I-branch amplitude and the Q-branch comprising a Q-branchamplitude, of a QAM (quadrature amplitude modulation) modulation scheme;for each message element, calculating the received wave amplitudeaccording to a square root of a sum of the I-branch amplitude squaredplus the Q-branch amplitude squared, and calculating the received wavephase according to an arctangent of a ratio of the Q-branch amplitudedivided by the I-branch amplitude; and demodulating the message byselecting a particular amplitude level, of the Namp amplitude levels,closest to the received wave amplitude, and selecting a particular phaselevel, of the Nphase phase levels, closest to the received wave phase.

In another aspect, there is a method for a transmitter of a base stationof a wireless network to mitigate message faults, the method comprising:using a modulation scheme comprising amplitude modulation multiplexedwith phase modulation, the amplitude modulation according to integerNamp amplitude levels and the phase modulation according to integerNphase phase modulation levels; determining a rate of amplitude faultsand phase faults, wherein an amplitude fault comprises a messagemodulated, by the transmitter, according to a particular amplitude levelof the Namp amplitude levels, and then demodulated, by a receiver,according to a different amplitude level, and wherein a phase faultcomprises a message modulated, by the transmitter, according to aparticular phase level of the Nphase phase levels, and then demodulated,by a receiver, according to a different phase level; selecting a secondmodulation scheme comprising integer Mamp amplitude levels and integerMphase phase levels, wherein Mamp and Mphase are selected according tothe rate of amplitude faults and the rate of phase faults; and whereineither Mamp is different from Namp, or Mphase is different from Nphase,or both.

In another aspect, there is a method for a wireless transmitter tooptimize communication throughput, the method comprising: using a firstmodulation scheme comprising amplitude modulation multiplexed with phasemodulation, the amplitude modulation according to integer Namp amplitudelevels and the phase modulation according to a first plurality of phaselevels, wherein the phase levels of the first plurality are uniformlyspaced apart by a first phase separation; determining a rate of phasefaults, wherein a phase fault comprises a message transmitted, by thetransmitter, according to a particular phase level of the firstplurality, and demodulated, by a receiver, according to a differentphase level than the particular phase level; and when the rate of phasefaults exceeds a predetermined threshold, changing to a secondmodulation scheme comprising a second plurality of phase levelsuniformly spaced apart by a second phase separation, wherein the secondphase separation is larger than the first phase separation.

This Summary is provided to introduce a selection of concepts in asimplified form. The concepts are further described in the DetailedDescription section. Elements or steps other than those described inthis Summary are possible, and no element or step is necessarilyrequired. This Summary is not intended to identify key features oressential features of the claimed subject matter, nor is it intended foruse as an aid in determining the scope of the claimed subject matter.The claimed subject matter is not limited to implementations that solveany or all disadvantages noted in any part of this disclosure.

These and other embodiments are described in further detail withreference to the figures and accompanying detailed description asprovided below.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1A is a schematic showing an exemplary embodiment of a 16QAMconstellation chart with orthogonal amplitude-modulated branches,according to some embodiments.

FIG. 1B is a polar plot showing an exemplary embodiment of the overallwave amplitude and phase of 16QAM states, according to prior art.

FIG. 1C is a schematic showing an exemplary embodiment of aconstellation chart of the states of FIG. 1A including phase noise,demodulated according to orthogonal amplitude-modulated branches,according to some embodiments.

FIG. 2A is a schematic showing an exemplary embodiment of a modulationscheme with multiplexed amplitude and phase modulation, according tosome embodiments.

FIG. 2B is a polar plot showing an exemplary embodiment of the overallwave amplitude and phase of the states of FIG. 2A, according to someembodiments.

FIG. 2C is a schematic showing an exemplary embodiment of aconstellation chart of the states of FIG. 2A, but demodulated accordingto orthogonal amplitude-modulated branches, according to someembodiments.

FIG. 3 is a schematic showing an exemplary embodiment of a wavemodulated according to overall amplitude and phase, and the same wavedecomposed into orthogonal branches, according to some embodiments.

FIG. 4 is an flowchart showing an exemplary embodiment of a method totransmit a message modulated according to wave amplitude and phase, andthen receive the message using quadrature components, according to someembodiments.

FIG. 5A is an exemplary embodiment of a constellation chart showing thereceived states of FIG. 2C including phase noise, according to someembodiments.

FIG. 5B is an exemplary embodiment of a constellation chart showing thereceived states of FIG. 2C including amplitude noise, according to someembodiments.

FIG. 6 is a flowchart showing an exemplary embodiment of a procedure formodulating a message according to overall wave amplitude and phase,receiving the message according to orthogonal branch amplitudes, andcorrecting amplitude noise and phase noise, according to someembodiments.

FIG. 7A is a modulation table showing an exemplary embodiment of statesmodulated according to a non-square modulation scheme with three phaselevels, according to some embodiments.

FIG. 7B is a polar plot showing an exemplary embodiment of statesmodulated according to a non-square modulation scheme with three phaselevels, according to some embodiments.

FIG. 7C is a constellation chart showing an exemplary embodiment ofstates modulated according to a non-square modulation scheme with threephase levels, and demodulated according to orthogonal branch amplitudes,according to some embodiments.

FIG. 8A is a modulation table showing an exemplary embodiment of statesmodulated according to a non-square modulation scheme with two phaselevels, according to some embodiments.

FIG. 8B is a polar plot showing an exemplary embodiment of statesmodulated according to a non-square modulation scheme with two phaselevels, according to some embodiments.

FIG. 8C is a constellation chart showing an exemplary embodiment ofstates modulated according to a non-square modulation scheme with twophase levels, and demodulated according to orthogonal branch amplitudes,according to some embodiments.

Like reference numerals refer to like elements throughout.

DETAILED DESCRIPTION

Systems and methods disclosed herein (the “systems” and “methods”, alsooccasionally termed “embodiments” or “arrangements” or “versions” or“examples”, generally according to present principles) can provideurgently needed wireless communication protocols for mitigating theeffects of phase noise at high frequencies planned for late 5G and 6Gcommunications. Disclosed herein are methods to prepare and transmit amessage according to a first modulation scheme, and then to receive anddemodulate the message according to a second modulation scheme withdifferent properties. The first modulation scheme, in some embodiments,is multiplexed amplitude and phase modulation, which can be configuredto provide enhanced phase-noise margins and versatility, especially forgenerating advantageous non-square modulation schemes. The secondmodulation scheme, in some embodiments, uses two orthogonalamplitude-modulated branches, which may provide convenient signalprocessing of quadrature components, as opposed to processing the wholereceived wave. Examples show how using two different modulation schemesfor transmission and reception can enable mitigation of phase noise andamplitude noise. Further examples show how to diagnose message faultsaccording to the amplitude and phase deviations of the demodulatedsignals, and how to select a particular modulation scheme to combatobserved fault types, including phase faults.

The examples presented below are suitable for adoption by a wirelessstandards organization. Advanced modulation options configured toprovide large phase margins, when presented as a wireless standard, mayenable future wireless users to access high-frequency bands that wouldotherwise be precluded due to phase noise, as well as enhancedreliability in low-medium frequency bands, at zero or negligible cost inpower and resources.

Terms herein generally follow 3GPP (third generation partnershipproject) standards, but with clarification where needed to resolveambiguities. As used herein, “5G” represents fifth-generation, and “6G”sixth-generation, wireless technology in which a network (or cell or LANLocal Area Network or RAN Radio Access Network or the like) may includea base station (or gNB or generation-node-B or eNB or evolution-node-Bor AP Access Point) in signal communication with a plurality of userdevices (or UE or User Equipment or user nodes or terminals or wirelesstransmit-receive units) and operationally connected to a core network(CN) which handles non-radio tasks, such as administration, and isusually connected to a larger network such as the Internet. Thetime-frequency space is generally configured as a “resource grid”including a number of “resource elements”, each resource element being aspecific unit of time termed a “symbol period” or “symbol-time”, and aspecific frequency and bandwidth termed a “subcarrier” (or “subchannel”in some references). Symbol periods may be termed “OFDM symbols”(Orthogonal Frequency-Division Multiplexing) in references. The timedomain may be divided into ten-millisecond frames, one-millisecondsubframes, and some number of slots, each slot including 14 symbolperiods. The number of slots per subframe ranges from 1 to 8 dependingon the “numerology” selected. The frequency axis is divided into“resource blocks” (also termed “resource element groups” or “REG” or“channels” in references) including 12 subcarriers, each subcarrier at aslightly different frequency. The “numerology” of a resource gridcorresponds to the subcarrier spacing in the frequency domain.Subcarrier spacings of 15, 30, 60, 120, and 240 kHz are defined invarious numerologies. Each subcarrier can be independently modulated toconvey message information. Thus a resource element, spanning a singlesymbol period in time and a single subcarrier in frequency, is thesmallest unit of a message. “Classical” amplitude-phase modulationrefers to message elements modulated in both amplitude and phase,whereas “quadrature” or “PAM” (pulse-amplitude) modulation refers to twosignals, separately amplitude-modulated, and then multiplexed andtransmitted with a 90-degree phase shift between them. The two signalsmay be called the “I” and “Q” branch signals (for In-phase andQuadrature-phase) or “real and imaginary” among others. Standardmodulation schemes in 5G and 6G include BPSK (binary phase-shiftkeying), QPSK (quad phase-shift keying), 16QAM (quadrature amplitudemodulation with 16 modulation states), 64QAM, 256QAM and higher orders.Most of the examples below relate to QPSK or 16QAM, with straightforwardextension to the other levels of modulation. QPSK is phase modulated butnot amplitude modulated. 16QAM may be modulated according to PAM whichexhibits two phase levels at zero and 90 degrees (or in practice, forcarrier suppression, ±45 degrees) and four amplitude levels includingtwo positive and two negative amplitude levels, thus forming 16 distinctmodulation states. For comparison, classical amplitude-phase modulationwith 16 states includes four positive amplitude levels and four phasesof the overall wave signal, which are multiplexed to produce the 16states of the modulation scheme. “SNR” (signal-to-noise ratio) and“SINR” (signal-to-interference-and-noise ratio) are used interchangeablyunless specifically indicated. “RRC” (radio resource control) is acontrol-type message from a base station to a user device.“Digitization” refers to repeatedly measuring a waveform using, forexample, a fast ADC (analog-to-digital converter) or the like. An “RFmixer” is a device for multiplying an incoming signal with a localoscillator signal, thereby selecting one component of the incomingsignal.

In addition to the 3GPP terms, the following terms are defined herein.Although in references a modulated resource element of a message may bereferred to as a “symbol”, this may be confused with the same term for atime interval (“symbol-time”), among other things. Therefore, eachmodulated resource element of a message is referred to as a “modulatedmessage resource element”, or more simply as a “message element”, inexamples below. A “demodulation reference” is one or more modulated“reference resource elements” or “reference elements” modulatedaccording to the modulation scheme of the message and configured toexhibit levels of the modulation scheme (as opposed to conveying data).A “calibration set” is one or more predetermined amplitude levels and/orphase levels of a modulation scheme, typically determined by a receiverfrom a demodulation reference. A “short-form” demodulation reference isa demodulation reference that exhibits only selected amplitude levels,such as the maximum and/or minimum amplitude levels, of the modulationscheme, from which the receiver can determine any intermediate levels bycalculation. “RF” or radio-frequency refers to electromagnetic waves inthe MHz (megahertz) or GHz (gigahertz) frequency ranges. The “raw” or“overall” or “waveform” signal is the as-received waveform beforeseparation of the quadrature branch signals, and includes a raw-signalamplitude and a raw-signal phase. “Phase noise” is random noise or timejitter that alters the overall phase of a received signal, usuallywithout significantly affecting the overall amplitude. “Phase-noisetolerance” or “phase-noise margin” is a measure of how much phasealteration can be imposed on a message element without causing ademodulation fault. “Amplitude noise” includes any noise or interferencethat primarily affects amplitudes of received signals. Interference dueto competing signals is treated as noise herein, unless otherwisespecified. A “faulted” message has at least one incorrectly demodulatedmessage element. A “phase fault” is a message element demodulated as astate differing in phase from the intended modulation state, whereas an“amplitude fault” is a message element demodulated as a state differingin amplitude from the intended modulation state.

Referring to quadrature or QAM or PAM modulation, an “I-Q” space is anabstract two-dimensional space defined by an I-branch amplitude and anorthogonal Q-branch amplitude, in which each transmitted message elementoccupies one of several predetermined I-Q states of a modulation scheme.The orthogonal branches are sometimes called “real” and “imaginary”, andthe I-Q space is sometimes called the “complex plane”. The incomingsignal to the receiver may be termed the “overall” waveform or signal,which includes an “overall amplitude” and an “overall phase”. Thereceiver can then process the overall signal by separating it into twoorthogonal branches as mentioned. The receiver can also combine thebranch amplitudes to determine a “sum-signal”, which is the vector sumof the I and Q branch signals and generally approximates the overallwaveform. A vector sum is a sum of two vectors, which in this caserepresent the amplitudes and phases of the two orthogonal branches inI-Q space. The sum-signal has a “sum-signal amplitude”, equal to thesquare root of the sum of the I and Q branch amplitudes squared (the“root-sum-square” of I and Q), and a “sum-signal phase”, equal to thearctangent of the ratio of the I and Q signal amplitudes (plus anoptional base phase, ignored herein). Thus the sum-signal represents theoverall received waveform, aside from signal processing errors in thereceiver—which are generally negligible and are ignored herein.

When the message element is received at a receiver, the signal may besubstantially different from the transmitted wave due to added phasenoise and amplitude noise. Normally the receiver separates the receivedwave into orthogonal I and Q branches which are affected in complex waysby the noise. Examples below show (a) how the transmitted signal can bemodulated to provide enhanced phase-noise or amplitude-noise margins,(b) how the receiver can quantitatively determine the amplitude andphase noise effects, and (c) how the receiver can subtract amplitude andphase noise from the received message. Further examples show how anetwork can monitor various types of noise, and can select a differentmodulation scheme (such as a non-square modulation scheme) to combatspecific noise problems.

Most of the examples are presented using 16QAM and the correspondingmultiplexed amplitude-phase modulation scheme of 16 states, however theprinciples and conclusions apply equally to higher-order QAM, otherquadrature modulation schemes, and many other modulation schemes ingeneral.

Turning now to the figures, examples show how modulation schemes aresusceptible to phase noise at high frequencies.

FIG. 1A is a schematic showing an exemplary embodiment of a 16QAMconstellation chart, according to some embodiments. As depicted in thisnon-limiting example, a modulation scheme 101 includes 16 allowedmodulation states 102, each allowed state determined by an I-branchsignal and a Q-branch signal orthogonal to the I-branch signal (forexample, the Q-branch phase-modulated at 90 degrees relative to theI-branch). The horizontal axis shows the amplitude modulation of theI-branch signal, and the vertical axis shows the amplitude modulation ofthe Q-branch signal. Each branch is amplitude-modulated at one of thepredetermined branch amplitude levels of the modulation scheme. In thiscase, the predetermined branch amplitude levels are −3, −1, +1, and +3(here and elsewhere, amplitudes are given in arbitrary units). Forexample, the distance 103 may be 1 unit, and the distance 104 may be 3units. The various branch amplitude levels are equally separated andsymmetrical around zero. The central cross-shape represents zeroamplitude. Negative branch amplitude levels are equivalent to a180-degree phase change. There are 16 states, as expected for 16QAM. Areceiver can receive a message element modulated according to thismodulation scheme, and can extract the I and Q branches separately byanalog or digital signal-processing means. The receiver can then measurethe amplitudes of those two branches, compare the measured amplitudevalues to a predetermined set of branch amplitude levels, select theclosest match to each of the message branch amplitude, and therebydetermine the modulation state of the message element. 16QAM encodes 4bits per message element.

The received waveform, before separation of the two branches, has anoverall amplitude 105 and an overall phase 106, as indicated for aparticular state 103. The overall amplitude 105 is the radius of thestate 103 from the origin, and the overall phase 106 is the anglerelative to the horizontal axis (ignoring carrier suppression, etc.).Thus each state 102, 103 can be described in terms of the I and Q branchamplitudes, or the overall amplitude and phase, depending on the task.

Each state 103 in the figure is represented as an icon shaded accordingto the overall amplitude, with dark gray for the lowest overallamplitude, light gray for the intermediate overall amplitude, and whitefor the highest overall amplitude. Although there are four branchamplitude levels in 16QAM, there are only three overall wave amplitudes,as indicated.

FIG. 1B is a polar plot showing an exemplary embodiment of the states of16QAM, according to some embodiments. As depicted in this non-limitingexample, the states of 16QAM are shaded as in the previous figure,according to the corresponding overall amplitude which is indicated bycircles 110, 111, 112. The lowest overall amplitude is shown as a smallcircle 112 and the four low-amplitude states are shown as dark gray dots113. The four states with the largest overall amplitude are shown aswhite dots 115 on the large circle 110. Eight states in 16QAM have thesame intermediate amplitude, as shown in light gray 114 on the middlecircle 111. Also shown is an arrow 118 indicating the overall amplitudeof a particular state 117, and an arc 116 indicating the overall phaseof the state 117.

The overall amplitude 118 equals the square root of the sum of thesquares of the I and Q branch amplitudes (that is, the “root-sum-square”of I and Q), while the overall phase 116 equals the arctangent of the Qamplitude divided by the I amplitude. To convert back to QAM, the Ibranch amplitude equals the overall amplitude 118 times the cosine ofthe overall phase 116, and the Q branch amplitude equals the overallamplitude 118 times the sine of the overall phase 116. Conversionbetween the quadrature parameters and the overall wave parameters isthus straightforward.

Although the branch amplitudes are modulated with four branch amplitudelevels in 16QAM, the actual transmitted waveform has only three distinctamplitudes, given by the three circles 110, 111, 112. This is becauseeight of the 16QAM states have the same overall amplitude. For 16QAM,the intermediate amplitude is 3.16 arbitrary units (that is,√(I²±Q²)=√(3²+1²)=3.16 for each of the gray dots 113). The threeamplitude values of the transmitted waveforms are not equally spaced, asshown by the three circles 110, 111, 112 having non-equally-spaced radii(specifically 1.41, 3.16, and 4.24 arbitrary units in this case). Thus,although the branch amplitudes are modulated according to four amplitudelevels, the transmitted and received wave has only three distinctamplitude levels, in 16QAM. The unequal spacing of the overall waveformamplitudes can limit the amplitude noise immunity, as described below.

Also shown is an arc-arrow 119 indicating the phase difference betweentwo of the intermediate-amplitude states. Due to the nonlinearities inQAM, that phase difference 119 is only 36.9 degrees. Due to the closespacing between adjacent states, 16QAM and the other QAM modulationschemes can result in phase faulting at high frequencies and high noiseenvironments.

FIG. 1C is a schematic showing an exemplary embodiment of the effect ofphase noise on a 16QAM constellation chart, according to someembodiments. As depicted in this non-limiting example, the modulationstates 122 of a 16QAM constellation chart 121 can be distorted angularly(“smeared out”) by phase noise in a characteristic way, as indicated byphase distortion clouds 128 which have an angular width as indicated byan arc-arrow 123. The depicted distortions would be caused by moderatephase noise at moderate frequencies; at high frequencies it is muchworse. If the same modulation scheme were attempted at the much higherfrequencies planned for future wireless operation, the phase noise wouldbe much larger than depicted, and the phase-noise clouds wouldsubstantially overlap, resulting in frequent message faults. Forexample, a particular pair of 16QAM states, indicated by an arc-arrow129, are separated by only 36.9 degrees of phase, as mentioned. Thislimits the phase noise tolerance of 16QAM, and indicates the need forstrategies to mitigate phase noise and enable communications at highfrequencies.

FIG. 2A is a schematic showing an exemplary embodiment of a modulationscheme with multiplexed amplitude and phase modulation, according tosome embodiments. As depicted in this non-limiting example, a modulationtable 201 includes 16 states 202, 205, 206 modulated in phase andamplitude of the overall waveform. The phase separation between adjacentstates is 90 degrees, as indicated by an arc-arrow 209. The depictedamplitude levels (1,2,3,4 units) and phase levels (45, 135, 225, 315degrees) are equally spaced apart. Hence, each state 202, 205, 206 isseparated by 90 degrees from its phase-adjacent neighbors, and by oneamplitude unit from its amplitude-adjacent neighbors. The icons of eachstate are shaded as white for the highest amplitude states, light grayfor the next-highest, then dark gray, then black for the lowestamplitude states.

Although the modulation table 201 appears similar to the constellationchart 101 of FIG. 1A, the meaning is quite different. The constellationchart 101 is a plot of the in-phase amplitude versus thequadrature-phase amplitude, whereas the modulation table 201 shows theoverall wave amplitude versus the overall wave phase. As demonstratedbelow, the two schemes (16QAM and multiplexed amplitude-phase modulationwith 16 states) provide the same bits per message element, but theydiffer greatly in their noise sensitivities.

FIG. 2B is a polar plot showing an exemplary embodiment of the overallwave amplitude and phase of the states of FIG. 2A, according to someembodiments. As depicted in this non-limiting example, circles 211, 212,213, 214 correspond to the four amplitudes of the modulation table 201,while four phase angles such as 219 correspond to the four phase levelsof the modulation table 201. The state icons are shaded in the same wasas in FIG. 2A, with white representing the highest amplitude 214, andblack representing the lowest amplitude 211. A particular state 215corresponds to state 205 in the previous figure. State 216 herecorresponds to state 206 in the previous figure, that is, the state withthe highest overall amplitude and highest overall phase. In addition,the polar plot shows that the lowest and highest phase levels are infact separated by the same phase angle (90 degrees) as the other phases,although the modulation table does not make that obvious The separationbetween phase-adjacent states is indicated by an arc-arrow 219.

FIG. 2C is a schematic showing an exemplary embodiment of aconstellation chart of the states of FIG. 2A, transmitted according tomultiplexed amplitude-phase modulation, but received and demodulatedaccording to orthogonal amplitude-modulated branches, according to someembodiments. As depicted in this non-limiting example, a constellationchart 221 of states 222 is shown as received and demodulated by areceiver. The constellation chart shows the I-branch amplitudes andQ-branch amplitudes of states 222 as received. Those states weremodulated, by the transmitter, in amplitude and phase (as in FIG. 2A),but then were demodulated by the receiver in orthogonal branchamplitudes (as in FIG. 1A).

The four radial groups correspond to each phase column of FIG. 2A. Forexample, state 225 here corresponds to states 215 and 205 in theprevious figures. State 226 here is the same as 216 and 206. The I and Qbranch amplitudes of state 225 are specifically called out as 224 and227. In contrast, the overall waveform amplitude of state 225 is shownas the radius line 228, and the overall waveform phase is given by theangle 223. Hence each state, originally modulated according toequally-spaced-apart amplitude levels and equally-spaced-apart phaselevels of the overall waveform, now appear as the resulting I and Qamplitudes of the figure.

The constellation chart of FIG. 2C provides larger phase-noise marginsthan 16QAM, as shown by the arc-angle 229. Specifically, the phaseseparation between adjacent phase states is 90 degrees here, whereas theclosest phase separation is only 36.9 degrees when they were modulatedaccording to QAM (such as 129 in FIG. 1C). The improved phaseseparations are preserved in the final demodulated states, whether thereceiver demodulates according to the overall amplitude-phase or by QAM.

The modulation scheme of FIG. 2C includes 16 states which are originallymodulated as the amplitude and phase of the overall waveform, andtransmitted as a sine wave with that amplitude and phase. The sine wavewas then received by a receiver and demodulated according to orthogonalbranch amplitudes, with the I and Q branch amplitudes as shown. Sincethis scheme provides noise margins greater, by a factor of 2.4, greaterthan 16QAM, it may be suitable for high-frequency communications wherethe QAM schemes are prohibited due to phase faulting.

In addition, the amplitude levels are equally spaced apart as shown. Thestates originally modulated as multiplexed amplitude-phase, and thendemodulated as orthogonal branches, are equally-spaced-apart in both theI and Q directions, as well as in the overall wave amplitude. Incontrast, the overall amplitude states of 16QAM are not equally spacedapart. The unequal separations between the overall amplitude levels of16QAM, and other QAM schemes in general, which impacts the amplitudenoise margin. As a further distinction, the number of overall amplitudelevels is four with multiplexed amplitude-phase modulation, but onlythree with quadrature modulation, as shown above.

The receiver can calibrate the predetermined branch amplitude levelsusing a demodulation reference proximate to the message. For example,the demodulation reference may be a short-form demodulation referencethat exhibits the maximum branch amplitudes of QAM and the maximumoverall waveform amplitude of multiplexed amplitude-phase modulation. Inthat case, a single short-form demodulation reference can be used tocalibrate both demodulation schemes, including the branch amplitudes ofQAM demodulation, and the overall waveform phase and amplitude levels.The overall waveform amplitude levels are generally √2 times thecorresponding branch amplitude levels.

The example demonstrates that enhanced phase noise margins can beobtained by modulating messages in equally-spaced amplitude and phaselevels of the transmitted wave, and then demodulated by the receiver inthe usual way, according to orthogonal I and Q branch amplitudes.Importantly, the wide phase separation between the phase-modulatedstates is preserved when the signal is demodulated according to QAM.

FIG. 3 is a schematic showing an exemplary embodiment of a wavemodulated according to overall amplitude and phase, and the same wavedecomposed into orthogonal branches, according to some embodiments. Asdepicted in this non-limiting example, a wave 301 is plotted versusphase (or equivalently, versus time) as modulated by a transmitter. Thewave 301 has a phase 302 (to the peak) and an amplitude 303 as shown.The particular wave configuration corresponds to state 206 in FIG. 2A,which in one scheme corresponds to a hexadecimal “D” in a messageelement.

A receiver has received this wave 301 and separated it into an I-branchcomponent 306 at zero degrees, plus a Q-branch component 307 at 90degrees. The I-branch amplitude 308 is the value 304 (box) of theoverall wave 301 at zero phase (where the Q-branch passes through zero).Likewise, the Q-branch amplitude 309 is the value 305 of the overallwave 301 at 90 degrees (where the I-branch passes through zero). Thusthe overall wave 301 is the sum of the two branch waves 306, 307.

The receiver, upon measuring the two branch amplitudes 308, 309, maydetermine that the I-branch amplitude 308 is maximally positive, whilethe Q-branch amplitude 309 is maximally negative, and therefore thereceived branch amplitudes correspond to state 226 of FIG. 2C, whichcorresponds to state 206 of FIG. 2A, which corresponds to a hex-D asmentioned. Thus the receiver can readily process a message that ismodulated in amplitude and phase but demodulated in two orthogonalbranch amplitude levels. The receiver can then determine the content ofthe message element by comparing the branch amplitudes to the set ofpredetermined branch amplitude levels, selecting the closest of thepredetermined branch amplitude levels in each case.

FIG. 4 is an flowchart showing an exemplary embodiment of a method totransmit a message modulated according to wave amplitude and phase, andthen receive the message using quadrature components, according to someembodiments. As depicted in this non-limiting example, at 401 atransmitter modulates each message element of a message usingmultiplexed amplitude-phase modulation, and transmits the message as aseries of sinusoidal waves, one sinusoidal wave per resource element,each sinusoidal wave having an overall amplitude and phase according tothe message content. At 402, a receiver receives the wave as an incomingsinusoidal signal, but does not demodulate the incoming signal itself.Instead, the receiver separates the incoming wave into two orthogonalbranches, the I-branch and the Q-branch. After some signal processing(frequency downconversion, filtering, limiting, digitization, subcarrierselection, etc.) the receiver measures the branch amplitudes of the Iand Q branches. At 403, the receiver demodulates the message element bycomparing the branch amplitudes to a calibration set containingpredetermined branch amplitude levels of the modulation scheme (asdetermined from a demodulation reference, for example), and selectingthe predetermined branch amplitudes closest to the measured I and Qbranch amplitudes of the received message element.

Thus the transmitter modulates each message element according to a firstmodulation scheme involving multiplexed amplitude and phase modulation,and thereby provides a wide phase-noise margin equal to the separationbetween the modulated phase levels. The receiver then receives thetransmitted wave and demodulates the message element according to asecond modulation scheme involving orthogonal branch amplitudes.Receivers generally use orthogonal branch signals for signal processingand demodulation because this is an economical and effective way to dosignal processing. The receiver thereby determines the message contentwhile mitigating phase noise (due to the large phase level separations)and at low cost (by separately processing orthogonal components).

FIG. 5A is an exemplary embodiment of a constellation chart showing thereceived states of FIG. 2C, but now including phase noise, according tosome embodiments. As depicted in this non-limiting example, aconstellation chart such as 221 has been distorted by phase noise. Inthis case, and many cases of interest at high frequencies, the phasenoise is due to clock errors and the like, which affect the phase of allmodulation states in a similar way: rotating the phase of the state by aphase rotation angle which is proportional to the phase noise. Dots 501indicate the undistorted modulation states as they would be received bya receiver if there were no phase noise, and little circles 503 indicatethe same states rotated by phase noise.

The message is modulated in amplitude and phase of the overall waveformby the transmitter, and demodulated according to quadrature amplitudedemodulation by the receiver. However, phase noise does not directlyaffect the I and Q branches; it directly rotates the overall phase ofthe incoming wave, and this results secondarily in changes to the I andQ amplitudes. As shown, the phase rotation angle 502 affects all of themodulation states in the same way, by rotating them to the distortedpositions indicated by little circles 503.

The receiver can mitigate this phase noise by reversing the phaserotation (aside from high-order effects and receiver nonlinearitieswhich are generally small and are ignored herein). First, the receivercan receive a demodulation reference proximate to the message, whereinthe demodulation reference has a specific predetermined modulation whichis known to the receiver. The receiver can determine the phase rotationangle by measuring the demodulation reference, and can then correct eachof the I and Q branch amplitudes of the message elements bymathematically de-rotating them, specifically by calculating the I and Qamplitudes with the phase rotation reversed.

For example, regarding state 501, the receiver can calculate thedistortion in the I-branch 505 according to the phase rotation angle 502and the original phase angle 506 (here, 45 degrees), and can subtractthat I-branch distortion 505 from the received I-branch amplitude.Likewise, the receiver can calculate the Q-branch distortion 504 andsubtract it from the received Q-branch amplitude, thereby recovering theoriginal, undistorted I and Q amplitudes of the original state 501.Geometrical formulas or algorithms can be used to calculate the I-branchand Q-branch distortions 505, 504 according to the received I-branch andQ-branch amplitudes and the phase rotation angle. Alternatively,formulas or algorithms can be used to calculate the corrected I-branchand Q-branch amplitudes directly. As a further alternative, the receivercan calculate the overall wave amplitude and phase corresponding to thereceived I and Q signals, subtract the phase rotation angle from theoverall wave phase, and then calculate the corrected I-branch andQ-branch amplitudes accordingly. There are many other ways to implementthe phase correction, all foreseen.

As an alternative mitigation strategy, the receiver can measure theangular deviation of each message element, on the I-Q plane, relative tothe closest allowed state of the modulation scheme, and can average theangular deviations for a (preferably large) number of message elements,and thereby determine an estimate of the phase rotation angle. Thereceiver can then de-rotate those message elements by the estimatedphase rotation angle as described. Preferably the message elements areall simultaneous, such as multiple subcarrier signals in an OFDM symbol,which generally have the same phase noise effects. Depending on thebandwidth of the phase noise, the same or similar phase rotation anglecan be subtracted from other message elements in adjacent symbol-times.For example, if the phase noise does not vary substantially in onesymbol-time, the receiver can calculate a running average of theestimated phase rotation angles versus symbol, and may thereby improvethe accuracy of the phase noise mitigation.

FIG. 5B is an exemplary embodiment of a constellation chart showing thereceived states of FIG. 2C including amplitude noise, according to someembodiments. As depicted in this non-limiting example, the I and Qbranch amplitudes are distorted unidirectionally from the originalposition 511, to a distorted position 513. The amplitude noise causes anamplitude distortion by a distance 512. The amplitude noise is assumedto be at the same frequency as the message element but at a randomphase. The amplitude noise may be due to interference at the samefrequency, or it may be incoherent noise which has been extremelytightly filtered (by the subcarrier filter), thereby resulting in anarrow-band noise signal which is nearly equivalent to a synchronousinterference signal. In either case, the primary distortion is waveinterference. The wave interference includes both constructive anddestructive interference regions, depending on the relative phase. Inthe depicted case, the noise or interference is constructive in Quadrant1, destructive in Quadrant 3, and orthogonal (phase-shifting withminimal amplitude effect) in Quadrants 2 and 4. Hence, to sufficientaccuracy, the amplitude noise effect can be regarded as an amplitudeshift in a particular direction on the I-Q plane, for all of themodulation states (ignoring nonlinearities, as mentioned).

The receiver can negate the amplitude noise by first measuring theamplitude and phase of the noise as a “signal”, calculating themagnitude and direction of an amplitude shift 512 caused by the noise,calculating the I-branch and Q-branch components 514, 515 of theamplitude shift, and subtracting those branch components 514, 515 fromthe as-received I and Q branch amplitudes. In this way, the receiver candetermine corrected I and Q branch amplitudes, with the amplitude noiselargely negated. Since the transmitted signal was modulated according tothe amplitude and phase of the overall wave, the interference imposesthe same amplitude shift on all of the modulation states in aconstellation chart. Consequently, some of the modulation states areincreased by the interference, some are decreased, and some are hardlyaffected. The receiver, by determining the amplitude and phase of thenoise, can calculate those distortions and subtract them from thereceived I and Q amplitudes, and thereby recover the originallymodulated message elements.

FIG. 6 is a flowchart showing an exemplary embodiment of a procedure formodulating a message according to the overall wave amplitude and phase,receiving the message according to orthogonal branch amplitudes, andcorrecting amplitude noise and phase noise, according to someembodiments. As depicted in this non-limiting example, at 601 atransmitter transmits a short-form demodulation reference that includestwo resource elements, one exhibiting the maximum amplitude level of thefirst modulation scheme, and the other one a “gap” of no transmission.At 602, a receiver receives the demodulation reference and determinesseveral things about the noise: (a) the receiver measures phase noiseaccording to a phase rotation angle of the signal in themaximum-amplitude portion of the demodulation reference, (b) measures anoise level, including the noise amplitude and phase, according to asignal received during the no-transmission portion of the demodulationreference, and then (c) recalibrates the scale of the predeterminedamplitude levels according to the root-sum-square of the two branchamplitudes of the maximum-amplitude portion (since the root-sum-squareis unaffected by the phase rotation). For example, the receiver canmeasure a reference I-branch amplitude and a reference Q-branchamplitude from the signal in the first resource element of thedemodulation reference, and can determine the phase rotation angle froma ratio of the reference I-branch amplitude and the reference Q-branchamplitude. The receiver can then determine the amplitude and phase ofthe incoming noise or interference by measuring the noise I-branchamplitude and the noise Q-branch amplitude, of the noise signal thatarrives during the no-transmission message element of the demodulationreference, and thereby determine an amplitude shift and its componentsin the I and Q directions. Alternatively, the receiver can update thescale of the calibration set (of predetermined branch amplitude levels)according to the magnitude of the amplitude shift, specifically bycalculating a square root of a sum of the reference I-branch amplitudesquared plus the reference Q-branch amplitude squared. Other ways ofcalculating the amplitude and phase distortions based on thedemodulation reference, and applying them to the received branchamplitudes, are possible and foreseen.

At 603, the transmitter modulates a message according to a firstmodulation scheme that includes amplitude and phase modulation of eachmessage element. The transmitter modulates the overall transmitted waveaccording to a set of predetermined amplitude levels and phase levels.

At 604 the receiver receives the overall wave with its overall amplitudeand phase modulation, but now distorted by amplitude noise and phasenoise. The receiver then demodulates the message according to a secondmodulation scheme, different from the first modulation scheme. In thiscase, the receiver amplifies and filters the overall wave, thenseparates two orthogonal branch components, and measures their branchamplitudes. At 605, the receiver negates the phase noise by calculatinga corrected I branch amplitude and a corrected Q branch amplitude,according to the phase rotation angle. At 606, the receiver negates theamplitude noise by calculating a further corrected I branch amplitudeand a further corrected Q branch amplitude, according to the amplitudeand phase of the received noise signal in the gap of no transmission.

At 607, the receiver finishes the demodulation of each message elementby comparing the corrected branch amplitudes to the calibration set, ofpredetermined branch amplitude levels, of the second modulation scheme,and selecting the closest of the predetermined branch amplitude levelsfor each message element. The receiver can thus demodulate the message,while largely negating amplitude noise and phase noise. As a result,enhanced messaging reliability can be achieved, and high frequencycommunication bands can be opened, at zero or negligible cost.

In some embodiments, the signal processing steps may be reversed orchanged from those discussed, and other signal processing steps may beadded. It is immaterial how the receiver determines the branchamplitudes, so long as the measured branch amplitudes are related to thetransmitted overall wave plus noise.

FIG. 7A is a modulation table showing an exemplary embodiment of statesmodulated according to a non-square modulation scheme with three phaselevels, according to some embodiments. As depicted in this non-limitingexample, a modulation table 701 includes modulation states 702 in whichthe overall wave is modulated, by a transmitter, in amplitude and phase.The overall wave amplitude is modulated according to five equally spacedpredetermined amplitude levels, and the overall wave phase is modulatedaccording to three equally-spaced predetermined phases separated by 120degrees as indicated 709. Hence, the modulation scheme is non-squarebecause the number of phase levels is not equal to the number ofamplitude levels. Icons are shaded from black for the lowest amplitudeto white for the highest amplitude. The phase separation is 30 degreeslarger than the phase separation of a square 16-state modulation schemesuch as that of FIG. 2A, and this extra phase separation provides awider phase noise margin, which may enable higher frequencycommunications. In addition, the added amplitude level enhancesthroughput. The 15 modulation states shown here almost matches the 16states of, for example, 16QAM, and therefore the size of messagesmodulated according to the depicted scheme are only slightly longer thanfor 16QAM or the other 16-state modulation schemes. Due to the largephase noise margin of 120 degrees, communications are enabled inhigh-frequency bands that would be prohibited to 16QAM due to frequentphase faults.

FIG. 7B is a polar plot showing an exemplary embodiment of statesmodulated according to a non-square modulation scheme with three phaselevels, according to some embodiments. As depicted in this non-limitingexample, the states 710, corresponding to the states of the previousfigure, are shown versus phase angle, with five circles 711, 712, 713,714, 715 indicating the amplitude levels. As indicated by an arc-arrow719, the spacing between phase levels is 120 degrees. The icons here areshaded in the same way as in FIG. 7A. This three-phase modulation schememay be advantageous if prior-art modulation schemes result in excessiverates of phase faulting, and the extra amplitude level may be acceptableif there is little amplitude faulting.

FIG. 7C is a constellation chart showing an exemplary embodiment ofstates modulated according to a non-square modulation scheme with threephase levels and five amplitude levels, and then demodulated accordingto two orthogonal amplitude-modulated branch signals, according to someembodiments. As depicted in this non-limiting example, the depictedmodulation scheme may be invoked if a receiver has encountered excessivephase faults when using a modulation scheme that provides only 90-degreephase-noise margin. For wider phase noise tolerance, the transmitter hasswitched to the modulation scheme of FIG. 7A or 7B, in which the overallwaveform states 721 are phase-modulated according to three predeterminedphase levels separated by 120 degrees, as shown by the angle 729. Thelarger phase separation between the phase levels thereby enables thereceiver to avoid most phase noise faults. In addition, the number ofamplitude levels in the amplitude modulation of the overall wave wasincreased from four to five, to maintain sufficient throughput. Asmentioned, the number of states is now 3×5=15 states, only slightly lessthan the 16 states of the previous modulation scheme. The asymmetricmodulation scheme therefore provides almost the same information contentper message element as the 16-state square modulation schemes.

In most cases, the lowest fault rate can be obtained by adjusting themodulation scheme so that the rates of phase faults and amplitude faultsare approximately equal. When the rate of amplitude faults is much lowerthan the rate of phase faults, the additional amplitude level mayprovide needed throughput without causing excessive faulting.

Before switching to the 120-degree modulation scheme, the transmittermay inform the receiver of the change, so that the receiver can beginusing the correct calibration set associated with the new modulationscheme. In this case, the receiver changes its tables of predeterminedbranch amplitude levels to those corresponding to the constellationchart depicted. Switching between the modulation scheme of FIG. 2A tothe one depicted here can be straightforward, because the signalprocessing and I-Q branch extraction and branch amplitude determinationsteps remain unchanged in the modulation switch. Only the finishingdemodulation step, such as step 607 of the flowchart above, is affectedby the changed modulation scheme, and that is merely changing to adifferent set of predetermined branch amplitude levels. However, thebranch amplitude levels in the depicted case would be different for thestates of different overall phase, since those at phase 180 degrees havelarger I-branch amplitude separations than states in the other two phasegroups. The receiver can readily accommodate those changes by including,in the calibration set, an indication of which predetermined branchamplitude levels to use for which overall phases.

FIG. 8A is a modulation table showing an exemplary embodiment of statesmodulated according to a non-square modulation scheme with two phaselevels, according to some embodiments. As depicted in this non-limitingexample, the asymmetric non-square modulation table 801 includes states802 that are amplitude modulated, by a transmitter, according to sixpredetermined amplitude levels, and phase modulated by two predeterminedphase levels as shown. Since Nphase is not equal to Namp, the table isnon-square. The shading again goes from black at the lowest amplitude upto white for the highest amplitude. This two-phase modulation schemeprovides a full 180 degrees of phase noise margin 809, which may bepreferred at the highest frequencies where the phase noise is expectedto be a seriously limiting factor.

FIG. 8B is a polar plot showing an exemplary embodiment of statesmodulated according to a non-square modulation scheme with two phaselevels, according to some embodiments. As depicted in this non-limitingexample, the states 812 correspond to those of the previous figure, onsix amplitude circles 811, and separated by a large phase separation819.

FIG. 8C is a constellation chart showing an exemplary embodiment ofstates modulated according to a non-square modulation scheme with twophase levels, and demodulated according to orthogonal branch amplitudes,according to some embodiments. As depicted in this non-limiting example,to combat excessive phase noise, the transmitter uses an especiallyphase-noise tolerant scheme in which the adjacent states 821 areseparated by 180 degrees as shown 829. Such a scheme may be advantageouswhen the rate of amplitude faulting remains low, thereby allowing thenumber of amplitude levels to be increased to six amplitude levels. Thenumber of states 821 is then 2×6=12 states. Messages are 33% longer thanwith the 16-state schemes on average, but with far more effective phasenoise mitigation.

Due to the many options and variations disclosed herein, and otherversions derived therefrom by artisans after reading this disclosure, itwould be helpful for a wireless standards committee to establishconventions governing formats and implementation options for modulationaccording to overall wave amplitude and phase, while demodulatingaccording to two orthogonal branch amplitudes, as disclosed. With such abeneficial modulation-demodulation scheme, future wireless users canenjoy phase-noise mitigation and amplitude-noise mitigation,transparently, with each communication.

The wireless embodiments of this disclosure may be aptly suited forcloud backup protection, according to some embodiments. Furthermore, thecloud backup can be provided cyber-security, such as blockchain, to lockor protect data, thereby preventing malevolent actors from makingchanges. The cyber-security may thereby avoid changes that, in someapplications, could result in hazards including lethal hazards, such asin applications related to traffic safety, electric grid management, lawenforcement, or national security.

In some embodiments, non-transitory computer-readable media may includeinstructions that, when executed by a computing environment, cause amethod to be performed, the method according to the principles disclosedherein. In some embodiments, the instructions (such as software orfirmware) may be upgradable or updatable, to provide additionalcapabilities and/or to fix errors and/or to remove securityvulnerabilities, among many other reasons for updating software. In someembodiments, the updates may be provided monthly, quarterly, annually,every 2 or 3 or 4 years, or upon other interval, or at the convenienceof the owner, for example. In some embodiments, the updates (especiallyupdates providing added capabilities) may be provided on a fee basis.The intent of the updates may be to cause the updated software toperform better than previously, and to thereby provide additional usersatisfaction.

The systems and methods may be fully implemented in any number ofcomputing devices. Typically, instructions are laid out on computerreadable media, generally non-transitory, and these instructions aresufficient to allow a processor in the computing device to implement themethod of the invention. The computer readable medium may be a harddrive or solid state storage having instructions that, when run, orsooner, are loaded into random access memory. Inputs to the application,e.g., from the plurality of users or from any one user, may be by anynumber of appropriate computer input devices. For example, users mayemploy vehicular controls, as well as a keyboard, mouse, touchscreen,joystick, trackpad, other pointing device, or any other such computerinput device to input data relevant to the calculations. Data may alsobe input by way of one or more sensors on the robot, an inserted memorychip, hard drive, flash drives, flash memory, optical media, magneticmedia, or any other type of file-storing medium. The outputs may bedelivered to a user by way of signals transmitted to robot steering andthrottle controls, a video graphics card or integrated graphics chipsetcoupled to a display that maybe seen by a user. Given this teaching, anynumber of other tangible outputs will also be understood to becontemplated by the invention. For example, outputs may be stored on amemory chip, hard drive, flash drives, flash memory, optical media,magnetic media, or any other type of output. It should also be notedthat the invention may be implemented on any number of different typesof computing devices, e.g., embedded systems and processors, personalcomputers, laptop computers, notebook computers, net book computers,handheld computers, personal digital assistants, mobile phones, smartphones, tablet computers, and also on devices specifically designed forthese purpose. In one implementation, a user of a smart phone orWi-Fi-connected device downloads a copy of the application to theirdevice from a server using a wireless Internet connection. Anappropriate authentication procedure and secure transaction process mayprovide for payment to be made to the seller. The application maydownload over the mobile connection, or over the Wi-Fi or other wirelessnetwork connection. The application may then be run by the user. Such anetworked system may provide a suitable computing environment for animplementation in which a plurality of users provide separate inputs tothe system and method.

It is to be understood that the foregoing description is not adefinition of the invention but is a description of one or morepreferred exemplary embodiments of the invention. The invention is notlimited to the particular embodiments(s) disclosed herein, but rather isdefined solely by the claims below. Furthermore, the statementscontained in the foregoing description relate to particular embodimentsand are not to be construed as limitations on the scope of the inventionor on the definition of terms used in the claims, except where a term orphrase is expressly defined above. Various other embodiments and variouschanges and modifications to the disclosed embodiment(s) will becomeapparent to those skilled in the art. For example, the specificcombination and order of steps is just one possibility, as the presentmethod may include a combination of steps that has fewer, greater, ordifferent steps than that shown here. All such other embodiments,changes, and modifications are intended to come within the scope of theappended claims.

As used in this specification and claims, the terms “for example”,“e.g.”, “for instance”, “such as”, and “like” and the terms“comprising”, “having”, “including”, and their other verb forms, whenused in conjunction with a listing of one or more components or otheritems, are each to be construed as open-ended, meaning that the listingis not to be considered as excluding other additional components oritems. Other terms are to be construed using their broadest reasonablemeaning unless they are used in a context that requires a differentinterpretation.

1. A method for a wireless receiver to demodulate a message, the methodcomprising: a) receiving a demodulation reference modulated, by atransmitter, according to an amplitude-phase modulation schemecomprising Namp amplitude levels and Nphase phase levels; b)determining, according to the demodulation reference, the Namp amplitudelevels and the Nphase phase levels of the amplitude-phase modulationscheme; c) receiving a message modulated, by the transmitter, accordingto the amplitude-phase modulation scheme, the message comprising messageelements, each message element comprising a resource element of aresource grid, wherein each message element, as received by the wirelessreceiver, contains a received wave comprising a received wave amplitudeand a received wave phase; d) for each message element, separating thereceived wave into an I-branch and an orthogonal Q-branch, the I-branchcomprising an I-branch amplitude and the Q-branch comprising a Q-branchamplitude, the I-branch and Q-branch comprising a QAM (quadratureamplitude modulation) modulation scheme; e) for each message element,calculating the received wave amplitude according to a square root of asum of the I-branch amplitude squared plus the Q-branch amplitudesquared, and calculating the received wave phase according to anarctangent of a ratio of the Q-branch amplitude divided by the I-branchamplitude; and f) demodulating the message by selecting a particularamplitude level, of the Namp amplitude levels, closest to the receivedwave amplitude, and selecting a particular phase level, of the Nphasephase levels, closest to the received wave phase.
 2. The method of claim1, wherein the message is received according to 5G or 6G technology. 3.The method of claim 1, wherein the amplitude-phase modulation schemecomprises amplitude modulation multiplexed with phase modulation.
 4. Themethod of claim 1, wherein the Namp amplitude levels are equally spacedapart in amplitude, and the Nphase phase modulation levels are equallyspaced apart in phase.
 5. The method of claim 1, wherein the Nphasephase modulation levels are equally spaced apart in phase, and whereinthe Namp amplitude levels are spaced apart unequally according to aformula.
 6. The method of claim 1, wherein Namp is different fromNphase.
 7. The method of claim 1, wherein the QAM modulation schemecomprises Nstate modulation states, wherein Nstate equals Namp timesNphase.
 8. The method of claim 1, wherein the separating the receivedwave into an I-branch and an orthogonal Q-branch comprises: a) measuringthe I-branch amplitude according to an in-phase component of thereceived wave; and b) measuring the Q-branch amplitude according to aquadrature-phase component of the received wave.
 9. The method of claim1, wherein: a) the demodulation reference comprises a first resourceelement and a second resource element; b) the first resource element ismodulated, by the transmitter, according to a maximum amplitude level ofthe Namp amplitude levels, multiplexed with a maximum phase level of theNphase phase levels; and c) the second resource element comprises zerotransmission.
 10. The method of claim 9, further comprising: a)measuring a received phase angle according to a received demodulationsignal in the first resource element of the demodulation reference; andb) determining a phase rotation angle comprising a difference betweenthe received phase angle and the maximum phase level of the Nphase phaselevels.
 11. The method of claim 10, further comprising: a) beforedemodulating each message element, subtracting the phase rotation anglefrom from the received wave phase of the message element.
 12. The methodof claim 9, further comprising: a) receiving a background signal in thesecond resource element of the demodulation reference; and b)determining a background amplitude of the background signal and abackground phase of the background signal.
 13. The method of claim 12,further comprising: a) for each message element, subtracting thebackground amplitude from the received wave amplitude when thebackground phase is aligned with the received wave phase, and adding thebackground amplitude to the received wave amplitude when the backgroundphase is opposite to the received wave phase.
 14. The method of claim12, further comprising, before calculating the received wave amplitudeand phase: a) for each message element, calculating an I-branchamplitude correction according to the background amplitude and thebackground phase, and calculating a Q-branch amplitude correctionaccording to the background amplitude and the background phase; and b)subtracting the I-branch amplitude correction from the I-branchamplitude, and subtracting the Q-branch amplitude correction from theQ-branch amplitude.
 15. A method for a transmitter of a base station ofa wireless network to mitigate message faults, the method comprising: a)using a modulation scheme comprising amplitude modulation multiplexedwith phase modulation, the amplitude modulation according to integerNamp amplitude levels and the phase modulation according to integerNphase phase modulation levels; b) determining a rate of amplitudefaults and a rate of phase faults, wherein an amplitude fault comprisesa message modulated, by the transmitter, according to a particularamplitude level of the Namp amplitude levels, and then demodulated, by areceiver, according to a different amplitude level of the Namp amplitudelevels, and wherein a phase fault comprises a message modulated, by thetransmitter, according to a particular phase level of the Nphase phaselevels, and then demodulated, by a receiver, according to a differentphase level of the Nphase phase levels; c) selecting a second modulationscheme comprising integer Mamp amplitude levels and integer Mphase phaselevels, wherein Mamp and Mphase are selected according to the rate ofamplitude faults and the rate of phase faults; and d) wherein eitherMamp is different from Namp, or Mphase is different from Nphase, orboth.
 16. The method of claim 15, wherein the selecting a secondmodulation scheme comprises: a) when the rate of amplitude faultsexceeds the rate of phase faults, selecting Mamp less than Namp; and b)when the rate of phase faults exceeds the rate of amplitude faults,selecting Mphase less than Nphase.
 17. The method of claim 15, whereinNamp is different from Nphase, or Mamp is different from Mphase, orboth.
 18. A method for a wireless transmitter to optimize communicationthroughput, the method comprising: a) using a first modulation schemecomprising amplitude modulation multiplexed with phase modulation, theamplitude modulation according to integer Namp amplitude levels and thephase modulation according to a first plurality of phase levels, whereinthe phase levels of the first plurality are uniformly spaced apart by afirst phase separation; b) determining a rate of phase faults, wherein aphase fault comprises a message transmitted, by the transmitter,according to a particular phase level of the first plurality, anddemodulated, by a receiver, according to a different phase level of thefirst plurality than the particular phase level; and c) when the rate ofphase faults exceeds a predetermined threshold, changing to a secondmodulation scheme comprising a second plurality of phase levelsuniformly spaced apart by a second phase separation, wherein the secondphase separation is larger than the first phase separation.
 19. Themethod of claim 18, further comprising: a) when the rate of phase faultsis less than a second predetermined threshold, changing to a thirdmodulation scheme comprising a third plurality of phase levels uniformlyspaced apart by a third phase separation, wherein the third phaseseparation is smaller than the first phase separation.
 20. The method ofclaim 18, further comprising: a) after changing to the second modulationscheme, determining a subsequent rate of phase faults; b) when thesubsequent rate of phase faults exceeds the first predeterminedthreshold, changing to a modulation scheme comprising amplitudemodulation according to integer Mamp amplitude levels, and phasemodulation according to a single phase modulation level.